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Fabricante

AD8061ART

Low-Cost, 300 MHz Rail-to-Rail Amplifiers

Analog Devices 

AD8061/AD8062/AD8063

Figure 8 shows a unity gain follower using the series resistor

strategy. The resistor isolates the output from the capacitance

and, more importantly, creates a zero in the feedback path that

compensates for the pole created by the output capacitance.

RSERIES

AD8061

VO

VIN

CLOAD

Figure 8. Series Resistor Isolating Capacitive Load

Voltage feedback amplifiers like those in AD806x family will be

able to drive more capacitive load without excessive peaking

when used in higher-gain configurations. This is because the

increased noise gain reduces the bandwidth of the overall feed-

back loop. Figure 9 plots the capacitance that produces 30%

overshoot versus noise gain for a typical amplifier.

10000

1000

RS = 4.7

RS = 0

100

10

1

2

3

4

5

CLOSED-LOOP GAIN

Figure 9. Capacitive Load vs. Closed-Loop Gain

DISABLE OPERATION

The internal circuit for the AD8063 disable function is shown in

Figure 10. When the DISABLE node is pulled below 2 V from

the positive supply, the supply current will decrease from typi-

cally 6.5 mA to under 400 µA, and the AD8063 output will

enter a high impedance state. If the DISABLE node is not con-

nected, and thus is allowed to float, the AD8063 will stay biased

at full power.

VCC

DISABLE

2V

TO AMPLIFIER

BIAS

VEE

Figure 10. Disable Circuit of the AD8063

TPC 28 shows AD8063 supply current versus DISABLE volt-

age. TPC 29 plots the output seen when the AD8063 input is

driven with a 10 MHz sine wave, and the DISABLE is toggled

from 0 V to 5 V, illustrating the part’s turn-on and turn-off time.

TPC 27 shows the input/output isolation response with the

AD8063 shut off.

BOARD LAYOUT CONSIDERATIONS

Maintaining the high-speed performance of the AD806x family

requires the use of high-speed board layout techniques and low

parasitic components.

The PCB should have a ground plane covering unused portions

of the component side of the board to provide a low impedance

path. The ground plane should be removed near the package to

reduce parasitic capacitance.

Proper bypassing is critical. A ceramic 0.1 µF chip capacitor

should be used to bypass both supplies, and be located within

3 mm of each power pin. An additional 4.7 µF to 10 µF tanta-

lum electrolytic capacitor should be connected in parallel to

provide charge for fast, large signal changes at the output.

Minimizing parasitic capacitance at the amplifier’s inverting

input pin is very important. The feedback resistor should be

located close to the inverting input pin. The value of the feed-

back resistor may come into play—for instance, 1 kΩ interacting

with 1 pF of parasitic capacitance creates a pole at 159 MHz.

Stripline design techniques should be used for signal traces

longer than 25 mm. These should be designed with either 50 Ω

or 75 Ω characteristic impedance and be properly terminated at

each end.

APPLICATIONS

Single Supply Sync Stripper

When a video signal contains synchronization pulses, it is

sometimes desirable to remove them prior to performing

certain operations. In the case of A-to-D conversion, the sync

pulses will consume some of the dynamic range, so removing

them will increase the converter’s available dynamic range for

the video information.

Figure 11 shows a basic circuit for creating a sync stripper using

the AD8061 powered by a single supply. When the nega-

tive supply is at ground potential, the lowest potential to

which the output can go is ground. This feature is exploited

to create a waveform whose lowest amplitude is the black level

of the video and does not include the sync level.

3V

VIDEO IN

75⍀

0.1␮F

3

7

AD8061 6

2

4 RF

1k⍀

RG

1k⍀

10␮F

75⍀

VIDEO OUT

75⍀

PIN NUMBERS ARE

FOR 8-PIN PACKAGE

Figure 11. Single 3 V Sync Stripper Using AD8061

In this case, the input video signal has its black level at ground,

so it comes out at ground at the input. Since the sync level is below

the black level, it will not show up at the output. However, all

of the active video portion of the waveform will be amplified

by a gain of two and then be normalized to unity gain by the

back-terminated transmission line. Figure 12 is an oscilloscope

plot of the input and output waveforms.

–14–

REV. C

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